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functional block diagram pin connections 14-pin epoxy dip (p-suffix) 16-pin sol (s-suffix) rev. a information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties which may result from its use. no license is granted by implication or otherwise under any patent or patent rights of analog devices. a dual audio analog switches ssm2402/ssm2412 one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 617/329-4700 fax: 617/326-8703 features clickless bilateral audio switching guaranteed break-before-make switching low distortion: 0.003% typ low noise: 1 nv/ ? hz superb off-isolation: 120 db typ low on-resistance: 60 v typ wide signal range: v s = 6 18 v; 10 v rms wide power supply range: 6 20 v max available in dice form general description the ssm2402/ssm2412 are dual analog switches designed spe- cifically for high performance audio applications. distortion and noise are negligible over the full audio operating range of 20 hz to 20 khz at signal levels of up to 10 v rms. the ssm2402/ ssm2412 offer a monolithic integrated alternative to expensive and noisy relays or complex discrete jfet circuits. unlike conven- tional general-purpose cmos switches, the ssm2402/ssm2412 provide superb fidelity without audio clicks during switching. conventional ttl or cmos logic can be used to control the switch state. no external pull-up resistors are needed. a t configuration provides superb off-isolation and true bilateral operation. the analog inputs and outputs are protected against overload and overvoltage. an important feature is the guaranteed break-before-make for all units, even ic-to-ic. in large systems with multiple switching channels, all separate switching units must open be- fore any switch goes into the on-state. with the ssm2402/ ssm2412, you can be certain that multiple circuits will all break-before-make. the ssm2402/ssm2412 represent a significant step forward in audio switching technology. distortion and switching noise are significantly reduced in the new ssm2402/ssm2412 bipolar- jfet switches relative to cmos switching technology. based on a new circuit topology that optimizes audio performance, the ssm2402/ssm2412 make use of a proprietary bipolar- jfet process with thin-film resistor network capability. nitride capacitors, which are very area efficient, are used for the propri- etary ramp generator that controls the switch resistance transi- tion. very wide bandwidth amplifiers control the gate-to-source voltage over the full audio operating range for each switch. the on-resistance remains constant with changes in signal amplitude and frequency, thus distortion is very low, less than 0.01% max. the ssm2402 is the first analog switch truly optimized for high-performance audio applications. for broadcasting and other switching applications which require a faster switching time, we recommend the ssm2412a dual analog switch with one-third of the switching time of the ssm2402. obsolete
rev. a C2C ssm2402/ssm2412Cspecifications electrical characteristics ssm2402/ssm2412 parameter symbol conditions min typ max units positive supply current +i sy v il = 0.8 v, 2.0 v 1 6.0 7.5 ma negative supply current Ci sy v il = 0.8 v, 2.0 v 1 4.8 6.0 ma ground current i gnd v il = 0.8 v, 2.0 v 1 0.6 1.5 ma digital input high v inh t a = full temperature range 20 v digital input low v inl t a = full temperature range 0.8 v logic input current i logic v in = 0 v to 15 v 2 1.0 5.0 m a analog voltage range 3 v analog C14.2 +14.2 v analog current range 3 i analog C10 +10 ma overvoltage input current v in = v supply 40 ma switch on resistance r on C14.2 v v a +14.2 v i a = 10 ma, v il = 2.0 v t a = +25 c6085 w t a = full temperature range 115 w tempco ( d r on / d t) 0.2 w / c r on match r on match C14.2 v v a +14.2 v 1 5 % i a = 10 ma, v il = 2.0 v switch on leakage current i s(on) v il = 2.0 v C14.2 v v a +14.2 v 0.05 1.0 m a v a = 0 v 0.05 10.0 na switch off leakage current i s(off) v il = 0.8 v C14.2 v v a +14.2 v 0.05 1.0 m a v a = 0 v 0.05 10.0 na turn-on time 4 t on v a = +10 v, r l = 2 k w ssm2402 10.0 ms t a = +25 c, see test circuit ssm2412 3.5 turn-off time 5 t off v a = +10 v, r l = 2 k w ssm2402 4.0 ms t a = +25 c, see test circuit ssm2412 1.5 break-before-make t off Ct on t a = +25 c ssm2402 6.0 ms time delay 6 ssm2412 2.0 charge injection q t a = +25 c ssm2402 50 pc ssm2412 150 on-st ate input cs (on) v a = 1 v rms 12 pf capacitance f = 5 khz, t a = +25 c off-st ate input cs (off) v a = 1 v rms 4 pf capacitance f = 5 khz, t a = +25 c off isolation i so(off) v a = 10 v rms, 20 hz to 20 khz 120 db t a = +25 c, see test circuit channel-to-channel c t v a = 10 v rms, 20 hz to 20 khz 96 db crosstalk t a = +25 c total harmonic thd 0 v to 10 v rms, 20 hz to 20 khz 0.003 0.01 % distortion 7 t a = +25 c, r l = 5 k w spectral noise density e n 20 hz to 20 khz, t a = +25 c 1 nv/ ? hz wideband noise density e n p-p 20 hz to 20 khz, t a = +25 c 0.2 m v p-p notes 1 v il is the logic control input. 2 current tested at v in = 0 v. this is the worst case condition. 3 guaranteed by r on test condition. 4 turn-on time is measured from the time the logic input reaches the 50% point to the time the output reaches 50% of the final value. 5 turn-off time is measured from the time the logic input reaches the 50% point to the time the output reaches 50% of the initial value. 6 switch is guaranteed by design to provide break-before-make operation. 7 thd guaranteed by design and dynamic r on testing. specifications subject to change without notice. (@ v s = 6 18 v, r l = open, and C40 8 c t a +85 8 c unless otherwise noted. all specifications, tables, graphs, and application data apply to both the ssm2402 and ssm2412, unless otherwise noted.) obsolete
ssm2402/ssm2412 rev. a C3C absolute maximum ratings operating temperature range . . . . . . . . . . . C40 c to +85 c operating supply voltage range . . . . . . . . . . . . . . . . . 20 v analog input voltage range continuous . . . . . . . . . . . . . . vC +3.5 v v a v+ C3.5 v maximum current through switch . . . . . . . . . . . . . . 20 ma logic input voltage range . . . . . . . . . . . . v+ supply to C2 v v+ supply to ground . . . . . . . . . . . . . . . . . . . . . . . . . . +36 v vC supply to ground . . . . . . . . . . . . . . . . . . . . . . . . . . . C20 v v a to vC supply . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +36 v package type u ja * u jc units 14-pin plastic dip (p) 76 33 c/w 16-pin sol (s) 92 27 c/w * q ja is specified for worst case mounting conditions, i.e., q ja is specified for device in socket for p-dip package; q ja is specified for device soldered to printed circuit board for sol package. timing diagram ordering guide temperature package model range description ssm2402p C40 c to +85 c 14-pin plastic dip ssm2402s C40 c to +85 c 16-pin sol ssm2412p C40 c to +85 c 14-pin plastic dip ssm2412s C40 c to +85 c 16-pin sol dice characteristics die size 0.105 0.097 inch, 10,185 sq. mils (2.667 2.464 mm, 6.57 sq. mm) wafer test limits parameter symbol conditions 1 limit units positive supply current +i sy v il = 0.8 v 7.5 ma max negative supply current Ci sy v il = 0.8 v 6.0 ma max ground current i gnd v il = 0.8 v 1.5 ma max logic input current i logic v in = 0 v 2 5.0 m a max switch on resistance r on C14.2 v v a +14.2 v 85 w max i a = 10 ma, v il = 2.0 v r on match between switches r on match C14.2 v v a +14.2 v 5 % max i a = 10 ma, v il = 2.0 v switch on leakage current i s(on) C14.2 v v a +14.2 v, v il = 2.0 v 1.0 m a max switch off leakage current i s(off) C14.2 v v a +14.2 v, v il = 0.8 v 1.0 m a max notes 1 v il = logic control input; v a = applied analog input voltage; i a = applied analog input current. 2 worst case condition. electrical tests are performed at wafer probe to the limits shown. due to variations in assembly methods and normal yield loss, yield after packaging is not guaranteed for standard product dice. consult factory to negotiate specifications based on dice lot qualifications through sample lot assembly and testing. obsolete
on resistance vs. analog voltage channel separation vs. frequency leakage current vs. analog voltage total harmonic distortion vs. frequency ssm2402 switching time vs. temperature supply current vs. temperature off isolation vs. frequency ssm2412 switching time vs. temperature overvoltage characteristics ssm2402/ssm2412Ctypical performance characteristics rev. a C4C obsolete
ssm2402/ssm2412 rev. a C5C ssm2402 t on /t off switching response ssm 2412 t on /t off switching response switching on/off transition t on /t off switching response test circuit switch on/off transition test circuit off isolation test circuit obsolete
ssm2402/ssm2412 rev. a C6C switching time test circuit simplified schematic obsolete
ssm2402/ssm2412 rev. a C7C applications information functional sections each half of the ssm2402/ssm2412 are made up of th ree major functional blocks: 1. t switch consists of jfet switches s 1 and s 2 in series as the main switches and switch s 3 as a shunt. 2. ramp generator generates a ramp voltage on command of the control input (see figure 1). a low-to-high ttl input at control input initiates a ramp that goes from approximately C7 v to +7 v in 12 ms. conversely, a high-to-low ttl transi- tion at control input will cause a downward ramp from ap- proximately +7 v to C7 v in 12 ms for the ssm2402, and 4 ms for the ssm2412. the ramp generator also supplies the +3 v and C3 v reference levels for switch control. 3. switch control the ramp from the ramp generator section is applied to two differential amplifiers (da 1 and da 2 ) in the switch control block. (see simplified schematic). one amplifier is refer- enced to C3 v and the other is referenced to +3 v. switch control outputs are: main switch control drives two 0.25 ma current sources that control the inverting inputs of each op amp. when on, the current sources cause a gate-to-source volt- age of approximately 2.5 v which is sufficient to turn off s 1 and s 2 . when the current sources from main switch control are off, each op amp acts as a unity-gain fol- lower (v gs = 0) and both switches (s 1 and s 2 ) will be on. shunt switch control controls the shunt switch of the t configuration. switch operation unlike conventional analog switches, the ssm2402/ssm2412 are designed to ramp on and off gradually over several millisec- onds. the soft transition prevents popping or clicking in audio systems. transients are minimized in active filters when the ssm2402/ssm2412 are used to switch component values. to see how the ssm2402/ssm2412 switches work, first con- sider an off-to-on transition. the control input is initially low and the ramp output is at approximately C7 v. the main switch control is high which drives current sources q 3 and q 4 to 0.25 ma each. these currents generate 2.5 v gate- to-source back bias for each jfet switch (s 1 and s 2 ) which holds them off. the shunt switch control is negative which holds the shunt jfet s 3 on. undesired feedthrough signals in the series jfet switches s 1 and s 2 are shunted to the negative supply rail through s 3 . figure 1. ramp generator figure 2. switch control when the control input goes from low to high, the ramp generator slews in the positive direction as shown in figure 2. when the ramp goes more positive than C3 v, the shunt switch control is pulled positive by differential amplifier da 2 which thereby puts shunt switch s 3 into the off state. note that s 1 and s 2 are still off, so at this time all three switches in the t are off. obsolete
ssm2402/ssm2412 rev. a C8C when the ramp output reaches +3 v, and the drive for the main switch control output is gated off by differential ampli- fier da 1 , current sources q 3 and q 4 go to the off state and the v gs of each main switch goes to zero. the high speed op amp followers provide essentially zero gate-to-source voltage over the full audio signal range; this in turn assures a constant low im- pedance in the on state over the full audio signal range. total time to turn on the ssm2402 switch is approximately 10.0 ms and 3.5 ms for the ssm2412. in systems using a large number of separate switches, there are advantages to having faster switching into off state than into the on state. break-before-make can be maintained at the sys- tem level. to see how the ssm2402/ssm2412 guarantee break-before-make, consider the on-to-off transition. a control input low initiates the on-to-off transition. the ramp generator integrates down from approximately +7 v to- wards C7 v. as the ramp goes through +3 v, the comparator controlling the main switches (s 1 and s 2 ) goes high and turns on current sources q 3 and q 4 which thereby puts s 1 and s 2 into the off state. at this time, all switches in the t are off. when the ramp integrates down to C3 v, the shunt switch con- trol changes state and pulls shunt switch s 3 into the on state. this completes the on-to-off transition; s 1 and s 2 are off, and s 3 is on to shunt away any undesired feedthrough. note though that the on-to-off time for main switches s 1 and s 2 is only the time interval required for the ramp to go from +7 v to +3 v, about 4 ms for the ssm2402, and 1.5 ms for the ssm2412. the time to turn on is about 2.5 times as long as the time to turn off. typical configuration the ssm2402/ssm2412 are much more than simple single solid state switches. the t configuration provides superb off-isolation through shunting of feedthrough via shunt switch s 3 . break-before-make is inherent in the design. the ramp pro- vides a controlled gating action that softens the on/off transi- tions. distortion is minimized by holding zero gate-to-source voltage for the two main fet switches, s 1 and s 2 , using the two op amp followers. figure 3 shows a distortion comparison be- tween the ssm2402 and a typical cmos switch. in summary, the ssm2402/ssm2412 are designed specifically for high per- formance audio system usage. overvoltage protection the ssm2402/ssm2412 are designed to guarantee correct op- eration with inputs of up to 14.2 v with 18 v supplies. the switch input should never be forced to go beyond the supply rails. in the off condition, if the inputs exceeds +14.2 v, there is a risk of turning the respective input pass fet on. when the input voltage rises to within 3.8 v of the positive supply, the op amp follower saturates and will not be able to maintain the full 2.5 v of back bias on the gate-to-source junction. under this condition, current will flow from the input through the shunt fet to the negative supply. this current is substantial, but is limited by the fet i dss . although this cur- rent will not damage the device, there is a danger of also turn- ing on the output pass fet, especially if the output is close to the negative rail. this risk of signal brea kthrough for inputs above +14.2 v can be eliminated by using a source resistor of 100 w C500 w in series with the analog input to provide additional current limiting. near the negative supply, transistors q 3 and q 4 saturate and can no longer keep the switch off. signal breakthrough can- not happen, but the danger here is latch-up via a path to vC through the shunt fet. additional circuitry (not shown) has been incorporated to turn off the shunt fet under these conditions, and the potential for latch-up is thereby eliminated. figure 3. comparison of the ssm2402 and typical cmos switch for distortion obsolete
ssm2402/ssm2412 rev. a C9C digitally-controlled attenuator figure 4 shows the usual approach to digitally-controlled at- tenuation. with s 1 closed, the signal passes unattenuated to the output. with s 1 open and s 2 closed, the signal is attenuated by r 1 and r 2 . the advantage of this configuration is that the at- tenuator current does not have to flow through the switches. the disadvantage is that the output is undefined during the switching period, which can be several milliseconds. the low distortion characteristics of the ssm2402/ssm2412 enable the alternate arrangement of figure 5 to be used. now only one switch is required to change between two gains, and there is always a signal path to the output. values for r 2 will typically be in the low kilohm range. for more gain steps and higher attenuation, the ladder arrange- ment of figure 6 can be used. this enables a wide dynamic range to be achieved without the need for large value resistors, which would result in degradation of the noise performance. figure 4. figure 5. figure 6. high performance stereo routing switcher the ssm2402 dual audio switch comprises the nucleus for this 16 channels-to-one high performance stereo audio routing switcher, which features negligible noise and low distortion over the frequency range of 20 hz to 20 khz. this performance is achieved even while driving 600 w loads at signal levels up to +30 dbu. the ssm2402 affords a much simplified electrical design and printed circuit board layout, along with reduced manufacturing cost, when compared with discrete jfet circuits of similar per- formance. the electrical performance of the design described is vastly superior to cmos switch designs, which are more prone to failure resulting from electrical static discharge. the switching control of the ssm2402 may be activated by conventional mechanical switches or 5 volt ttl or cmos logic circuits. the application shown utilizes a simple mechanical control switch for illustration purposes only. many diverse x/y control schemes, destination control, or computer controlled designs can be utilized. the t configuration of the ssm2402 switch provides excel- lent on-off isolation. the ssm2402 also features ms ramped turn on and ms ramped turn off for click-free switching. addi- tionally, the switch has a break-before-make switching sequence. both features become significant in large audio switching sys- tems where the audio path can pass through multiple switching elements. such controlled switching is very important in large systems used in broadcast program switching or in production work. the application circuit design also employs the ssm2015 bal- anced input amplifier (figure 7). the input impedance is high ( ? 100 k w ), balanced or unbalanced. the input circuit incorpo- rates a single pole rfi filter with a cutoff frequency set at 145 khz. in addition, the input circuit attenuates the signal by 25 db and extends the common-mode input voltage range to 98 volts peak, with common-mode rejection greater than 70 db from 20 hz to 20 khz. the ssm2015 is set to produce a 15 db gain. the signal drive level into the ssm2402 switch is then +10 dbu with a +20 dbu input level and +14 dbu peak, well within ideal operating range. good signal-to-noise is main- tained, with generous head-room available by electing to use 18 v dc power supply voltages. obsolete
ssm2402/ssm2412 rev. a C10C figure 7. switcher schematic obsolete
ssm2402/ssm2412 rev. a C11C figure 8. switcher functional block diagram overall performance of the 16 1 stereo switcher is noteworthy. input-to-output frequency response is flat to within 1 db over a 10 hz to 50 khz band. total harmonic distortion plus noise is less than 0.03%, from 20 hz to 20 khz. smpte intermodula- tion distortion is less than 0.02%. the use of 18 v dc power supplies produces a +30 dbm clip level, even when driving 600 w loads. table i. circuit performance specifications max input level +30 dbu input impedance, unbalanced 100 k w input impedance, balanced 200 k w common-mode rejection (20 hz to 20 khz) >70 db common-mode voltage limit 98 v peak max output level +30 dbu/dbm output impedance 67 w gain control range 2 db output voltage slew rate 6 v/ m s frequency response ( 0.05 db) 20 hz to 20 khz frequency response ( 0.5 db) 10 hz to 50 khz thd + noise (20 hz to 20 khz, +8 dbu) 0.005% thd + noise (20 hz to 20 khz, +24 dbu) 0.03% imd (smpte 60 hz & 4 khz, 4:1, +24 dbu) 0.02% crosstalk (20 hz to 20 khz) >80 db s/n ratio @ 0 db gain 135 db the routing switcher bus carries high level unbalanced audio, but is driven with low impedance sources. with the output im- pedance of the ssm2015 at virtually 0 w and the ssm2402 switch on, resistance is typically 60 w . bus-to-bus crosstalk is exceptionally low. for example, assuming 14 pf coupling be- tween buses and 20 khz signal, the crosstalk (isolation) exceeds 80 db. the 14 pf would be representative for the 16 1 stereo design shown. shielding of the buses with a printed circuit board ground plane and physically isolating the input and out- put circuits will reduce the crosstalk even further. the t con- figuration of the ssm2402 switch virtually eliminates crosstalk between the various input signal sources. the output amplifier incorporates a buffer amplifier that pro- vides 4 db of gain (nominally), with adjustable output level trim control. the buffer also isolates the switching bus from the bal- anced output amplifier circuit. the balanced output is designed to drive 600 w loads and utilizes two ssm2134 ic amplifiers. the differential design increases drive capability, yet increases the heat dissipation surface area, and keeps ic package tem- perature well within safe operating limits, even when driving 600 w loads. the ssm2134 is recommended due to its low noise, wide frequency response, and output drive current capabilities. obsolete
ssm2402/ssm2412 rev. a C12C outline dimensions dimensions shown in inches and (mm). 14-pin epoxy dip (p-suffix) 14 17 8 0.795 (20.19) 0.725 (18.42) 0.280 (7.11) 0.240 (6.10) pin 1 0.325 (8.25) 0.300 (7.62) 0.015 (0.381) 0.008 (0.204) 0.195 (4.95) 0.115 (2.93) seating plane 0.022 (0.558) 0.014 (0.356) 0.060 (1.52) 0.015 (0.38) 0.210 (5.33) max 0.130 (3.30) min 0.070 (1.77) 0.045 (1.15) 0.100 (2.54) bsc 0.160 (4.06) 0.115 (2.93) 16-pin sol (s-suffix) 16 9 8 1 0.4133 (10.50) 0.3977 (10.00) 0.4193 (10.65) 0.3937 (10.00) 0.2992 (7.60) 0.2914 (7.40) pin 1 seating plane 0.0118 (0.30) 0.0040 (0.10) 0.0192 (0.49) 0.0138 (0.35) 0.1043 (2.65) 0.0926 (2.35) 0.0500 (1.27) bsc 0.0125 (0.32) 0.0091 (0.23) 0.0500 (1.27) 0.0157 (0.40) 8 0 0.0291 (0.74) 0.0098 (0.25) x 45 printed in u.s.a. obsolete

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